Periodic Microstrip Leaky Wave Antenna with Double-Sided Shorting Pins and Pairs of Slots

A backward to forward scanning periodic microstrip leaky wave antenna (MLWA) is presented.)e proposed antenna consists of a long rectangular patch with alternating shorting pin on each side, which connects the antenna patch and the ground plane to form periodic shorting circuits. )ere are two pairs of slots alternately spaced on the long patch to suppress the open stop band (OSB). )e OSB problem was initially reduced by optimizing the structural parameters, and the slotting on the patch further improved it. )e measured radiation pattern in the y-z plane shows that the antenna can scan electronically from 142° to 39° toward the end-fire (+z direction) when the operating frequency changes from 6GHz to 12.9 GHz. )e measured gain is greater than 5 dBi over the entire operating band.


Introduction
Forward scanning microstrip leaky wave antenna (MLWA) first appeared in 1979 [1]. For more applications, microstrip periodic leaky wave antenna with forward and backward beam scanning capability was developed later [2].
A periodic MWLA is one in which there are multiple identical unit cells cascading along the propagation direction. e periodic structure is mainly composed of the following types of elements: strips (metallic strip [3], offset double-side parallel-strip line [4], and microstrip line [5]), stubs (open-ended stubs [6]), composite right/left handed [7], and slots [8]. However, periodic MLWAs have severe OSB problem at broadside. Various methods have been proposed to improve or eliminate OSB, including match the impedance within the unit cell [9,10], employing asymmetry [11], and using two similar but nonidentical elements per unit cell [12]. OSB can also be inhibited by optimizing structural parameters, such as optimizing the diameter of the cylindrical holes in the dielectric image line [13] and varying the groove width of the spoof plasmons cells [14]. ere are also some techniques to achieve broadside direction scanning, such as loading field-block structures [15][16][17][18].
Early years, a periodic half-width MLWA with backward to forward beam scanning capability is proposed in [19]. en, in [20], a half-width MLWA with the periodic short circuits is developed, which has a feature of narrower antenna width. However, the configuration of these antenna designs has cost a lot of shorting pins, leading to a low radiation efficiency and small gain since the reduction of effective radiation boundary. At the same time, they have poor broadside radiation.
In this paper, a periodic MLWA, composed of a uniform rectangle microstrip patch leaky wave antenna with shorting pins periodically alternately loaded on its side, is presented. e configuration of the antenna is shown in Figure 1. Slotting method is introduced for OSB suppression, because the slots in the patch can reduce mutual coupling between adjacent cells [21]. Figure 2 shows the specific location of the slots in each unit cell. e last shorting pin in the right unit is canceled for connecting the load port on the end of the antenna. A broadband matching is introduced for a better S-parameter through the overall bandwidth. Simulated and measured results of far-field radiation patterns, S-parameters, and gain are displaced.

Design Description
As an important improved design of [19,20], the proposed antenna proves that only a single shorting pin can form a periodic structure to achieve backward to forward beam scanning, instead of a series. In each periodic unit of length d, the distance between short-circuit pins on the same side of the patch is d, and the distance between short-circuit pins on different sides on the z-axis is d/2.

e Propagation Constant Achieved by Macrocell Method.
MLWA have the beam scanning capacity with a change in operating frequency, which is controlled by the complex propagation constants k zn . e complex propagation constant k zn of the periodic MLWAs is given by Floquet's theorem: where n is the order of the space harmonics (usually n � −1) and p is the period.     2 International Journal of Antennas and Propagation e direction of main beam is determined by the phase constant as follows: where θ is the direction of the main beam and k 0 is the wavenumber of the free space. e attenuation constant α zn is a parameter that indicates the amplitude or power attenuation of an electromagnetic or electrical signal during transmission. It is mainly related to the main beam and can be given by where θ HPBW is the half-power beam-width of the main beam. rough these formulas, the radiation performance of the antenna can be known from the propagation constant. It can be known from the dispersion diagram that the working mode of the proposed antenna is the first highorder mode. e periodic MLWA can scan from the backward (−z direction) to the forward (+z direction) because the β −1 can vary from negative values to positive values in Figure 3. e periodic structure can be seen as an infinite cascade of identical two-port networks [22], as shown in Figure 4. Each unit cell is characterized by the transmission matrix T: e propagation of a Bloch mode with wavenumber k z � β z − jα z corresponds to the condition: which shows that e −jk z p is an eigenvalue of the matrix T. However, the characterization of a single cell will neglect mutual coupling between adjacent cells. en, an integer number of unit cells, namely, macrocell, are introduced. An N-macrocell is modeled through the matrix T N , which can be calculated through the S-parameters by the conversion formulas. e S-parameters can be obtained by simulated or measured. e wavenumber k z,i can be given as [23] where λ N,i are eigenvalues of the matrix T N , N p is the distance between the ports of the network. Figures 5 and 6 are the normalized phase and attenuation constants calculated by equation (4) using the simulated S-parameters. As shown in Figure 5, when the distance between the two shorting pins on the same side d is changed from 28 mm to 20 mm, the phase constant curve is shifted to a higher frequency. e influence of the width of the antenna W on the phase constant is displayed in Figure 6. As W decreases from 13 mm to 7 mm, the phase constant curve moves to higher frequencies.

Structure Parameter Analysis.
is means the operating band shifts to a lower frequency band as d increases, and the increase in W causes a similar consequence.   In the process of changing the structural parameters, it was found that the OSB in this structure is related to the ratio of d/W. e OSB could be suppressed when the appropriate parameters are selected. Figure 7- erefore, a preliminary law that can effectively suppress OSB is obtained based on the simulation research. According to the ratio d/W, this structure can be divided into the following categories.
If d/W ≤ 1, the proposed antenna can only perform forward scanning because it is too dense to form a periodic structure, as shown in Figure 7.
Else if 1 < d/W ≤ 2, the proposed antenna can scan forward and backward but has obvious OSB, as shown in Figures 8 and 9.
Else if d/W > 2, the OSB will disappear, as shown in Figure 10.
However, the d/W range where the OSB does not exist is very small. e OSB will reappear when the ratio expanded further, as shown in Figure 11.

OSB Optimization.
e main manifestation of OSB is the serious degradation of the pattern when scanning through the broadside, and what shown in the phase constant curve is a stagnation around β � 0 and a sudden increase in the attenuation constant.
In order to further suppress the OSB, we etch two pairs of slots on the metal patch. e alternately spaced pairs of slot on the patch can change the impedance of the unit cell. After adjusting the width and length of each pair of the slot, the unit cells have been well matched. It may be diminished or suppressed by introducing two radiating elements in the periodic unit, or by adjusting the structural parameters to optimize the distance between the component pairs. Figure 12(a) and 12(b) are the electric field distribution of the proposed antenna without slots when the phase is 0 and 90 degrees, respectively. Figure 12(c) and 12(d) are the electric field distribution of the proposed antenna with slots when the phase is 0 and 90 degrees, respectively. It can be seen that both phases of the un-slotted antenna at the OSB frequency point show a significant standing wave behavior, that is, a nearly vertical zero potential. After slotting, the zero potential is no longer vertical, but a form of propagation. e almost standing wave behaviors are improved after etched pairs of slots on the patch, which means the performance of the MLWA around broadside have been better. Figure 13 is the normalized phase constants and S-parameter simulated by HFSS. It shows that the phase constant and S-parameter of the antenna will change when the dimensions of the slots on the patch change. By comparing the red and blue curves, it can be seen that, as L 1 increases, the OSB becomes serious and the phase constant curve moves slightly upward. e increase of L 2 also leads to the same      International Journal of Antennas and Propagation 5 results between the red the green curves. According to the red and black curve, the phase constant curve is unchanged as W 2 increases, but the OSB becomes more obvious. e same result can be obtained for the parameter W1 by comparing the red and magenta curves. In other words, the length of the slot has an effect on the phase curve, and the width of the slot can only affect the S-parameter. So, the performance of antenna can be optimized through varying the slot dimension. Figure 14 is the comparison of propagation constant of proposed antenna with and without slots. e antenna with slots has a smaller attenuation constant than the antenna without slots, especially near the OSB (around 8.3 GHz).
is shows that the slot on the antenna patch can indeed suppress the OSB. Figure 15(a) is a prototype of the proposed antenna, which is printed on a dielectric slab (relative dielectric constant εr � 2.45 and dielectric loss tangent tan δ � 0.005). e radius of each of these pins is 0.5 mm. Figure 15(b) shows the details of the pins and slots in the prototype antenna. Other values of parameters are listed in Table 1.

Measurement Results
e far-field radiation pattern of the proposed periodic MLWA in the y − z plane is measured. As described above, the antenna scans from −z direction to the +z direction through broadside with frequency increase. Figure 16 shows the measured and simulated normalized phase constants and attenuation constants. e measurement results are in good agreement with the simulation results. e phase constant curve varies smoothly and no OSB appears near the zero point of the curve. Figure 17 shows the measured pattern of backward quadrant and are pointed to θ � 137°, θ � 125°, and θ � 115°at 6.2 GHz, 6.6 GHz, and 7 GHz, respectively. It can be seen from Figure 18 that the antenna can radiate through the broadside direction, i.e, θ � 100°at 7.8 GHz, θ � 90°at 8.6 GHz, and θ � 80°at 9.4 GHz. When the operating frequency changes from 10.4 GHz to 12 GHz, the main beams scan from θ � 70°to θ � 51°in the forward quadrant, as displayed in Figure 19. Experimental results show that, as the operating frequency increases from 6 GHz to 12.9 GHz, the    main beam of the proposed antenna electronically and continuously scans from θ � 142°to θ � 39°in the y−z plane. e antenna performs well when scanning from backward to forward, even though the scanning beam passes through the broadside. e OSB has been suppressed.       [20]. It can be seen that the antenna in [20] has obvious OSB and regardless of radiation pattern or gain, and the OSB is basically invisible in the proposed antenna. e S-parameter of the forward scanning band of the proposed antenna is better than that of the backward. e gain of the proposed antenna is above 5 dBi when the operation frequency is higher than 6 GHz. Regardless of radiation pattern or gain, the OSB is basically invisible in the measurement results.
e comparison between the proposed antenna and previous work is shown in Table 2. e gain of the proposed antenna is greater than that of previous work. More importantly, the OSB in the antenna is nearly suppressed. e number of the pins was substantially reduced which resulted in a compact structure.

Conclusion
In this study, an improved MLWA with reduced shorting pins is submitted. e proposed antenna consists of shorting pins periodically loaded on both sides of the long rectangular patch, and the distance of each shorting pin on the z-axis is d/2. In order to suppress OSB, two pairs of slots are introduced in each unit. Experimental results show that, as the operating frequency increases from 6 GHz to 12.9 GHz, the main beam of the proposed antenna electronically and continuously scans from θ � 142°to θ � 39°in the y-z plane. is antenna design is simple, easy to manufacture, and can be useful in vehicle radar systems.

Data Availability
e data used to support the findings of this study are available from the corresponding author upon request.

Conflicts of Interest
e authors declare that they have no conflicts of interest.